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Slew-rate-enhanced rail-to-rail buffer
amplifier for TFT LCD data drivers
J.S. Kim, J.Y. Lee and B.D. Choi
A high-slew-rate low-power rail-to-rail buffer amplifier, which is suit-
able for thin film transistor liquid crystal display (TFT LCD) data driver
applications, is proposed. Previous dynamic biasing approaches
become ineffective as an output signal approaches VDD or VSS
supplies. However, the proposed buffer amplifier with a dynamic
biasing circuit enhances the slew rate throughout the entire rail-to-rail
signal range. The buffer amplifier and the previous counterparts were
fabricated in a 0.35 mm CMOS technology with 3.3 V supply
voltage. Measurements show that the slew rate for rail-to-rail signal
transition is enhanced from 0.80 V/ms of a previous counterpart to
2.75 V/ms.
Introduction: Higher resolution and frame frequency are required on
thin film transistor liquid crystal displays (TFT LCDs) for natural
motion picture and three-dimensional displays. The frame frequency
should be elevated from typically 60 to 480 Hz [1]. Consequently, the
driving time for each row must be decreased inverse proportionally,
and TFT LCD data drivers should be equipped with high-slew-rate
buffer amplifiers to accommodate the need for decreased driving time.
In addition, data drivers should have the rail-to-rail input range to
cover the liquid crystal driving voltage and also have the push-pull
output stage to support N-dot polarity inversion driving for high
image quality and low power consumption [2]. The rail-to-rail folded-
cascode class-AB amplifier in [3] is widely used to meet these
requirements.
Several buffer amplifiers for TFT LCD data drivers have been pro-
posed to enhance the slew rate with minimal increase in the quiescent
current [4– 7].In[4], the buffer amplifier uses comparators to sense
the slewing conditions, but it does not support the push-pull operation.
In [5], an additional current path is inserted, but the circuit requires a
clock signal, which increases the circuit complexity and power con-
sumption. The dynamic biasing circuits in [6] and [7] detect the
slewing conditions and turn on the auxiliary current sources. The
enhancement of the slew rate, however, ceases when the output
voltage approaches VDD or VSS, which degrades the overall slew rate
for the rail-to-rail signal swings. In this Letter, we propose a buffer
amplifier for a TFT LCD data driver with a dynamic current biasing
circuit that enhances the slew rate in the entire rail-to-rail signal range.
Limitations in dynamic biasing for slew rate enhancement: Fig. 1
shows a high-slew-rate amplifier with the dynamic biasing circuit [6].
At steady state, where V
IP
and V
IN
have the same voltage, M11 and
M12 are put in the triode region by appropriately sizing M11 and
M12 to turn off M13 and M14. In the transition state, all of the tail
current, IP, flows either through M9 or M10, which puts either M11
or M12 in the saturation region and turns on the dynamic current
source composed of M13 and M14. This transitional increase in the
tail current enhances the slew rate of the core amplifier.
VDD
IP
VIN VIP VIN VOUT
IN
IADD
VIP
VB
M10
M9
M5
M3
M1 M2
M8
M4
M6
M11 M12 M13
dynamic biasin
g
circuit core amplifier
M14
M7
Fig. 1 Slew-rate-enhanced amplifier with dynamic biasing circuit in [6]
In [7], as shown in Fig. 2, the concept of the dynamic biasing circuit
in [6] is applied to the buffer amplifier in [3] which is well suited for
TFT LCDs. Both dynamic current sources formed with the pairs of
M27, M28 and M29, M30, respectively, are used to support push-pull
operation. However, this slew-rate enhancement technique does not
fully function throughout the entire rail-to-rail signal range. For
example, when the input voltage in Fig. 2 at V
IP
rises from 0.3 to
3.0 V with 3.3 V supply voltage, M23 and M24 act as a slew detector
and add an extra current for M1 and M2 by turning on M29.
However, as the output voltage approaches 3.0 V, M23 and M24 are
turned off and stop working as a slew detector. A similar problem is
also observed when the input voltage falls from 3.0 to 0.3 V. This behav-
iour is especially pronounced in a high-to-high signal transition, for
example, 2.9 to 3.1 V, because M23 and M24 are turned off for the
signal. Similarly, behaviour is observed for a low-to-low signal tran-
sition. High-to-high or low-to-low signal transitions are indispensable
for N-dot inversion driving for high-image-quality and low-power
TFT LCDs [2].
VDD
VBP3
IN2
IP2
VIP VIN
IN1
Cc
VBP1
VOUT
VBN1
VBP2
IP1
VIP
VBN2
Cc
IADD,N
IADD,P
VBN3
VIN
M21
M19
M23 M24 M4 M3
VDD
VSS
M25 M26 M29 M30
VSS
VDD
M20
M2 M1 M7 M8
M9
M5 M6
M17
M10
M11
M14
M13 M18
M16
M15
core amplifierdynamic biasing circuit
M22 M27 M28
Fig. 2 Slew-rate-enhanced amplifier with dynamic biasing circuit in [7]
Proposed rail-to-rail slew-rate enhancement: The slew-rate enhance-
ment limited in the previous circuits in Figs 1 and 2originates in the
fact that the rise slewing is detected by PMOS transistors and the fall
slewing by NMOS transistors. The approach we employ to resolve
this problem uses NMOS and PMOS transistors in the construction of
the rise and fall slew detectors, respectively. The proposed amplifier
with an improved dynamic biasing circuit is shown in Fig. 3, where
the pairs of M19, M20 and M31, M32 form the rise and fall slew
detectors.
VDD
VBP3
VIN VIP
IADD,N
VIN
IN1 VIP
IP1
VBN2
Cc
Cc
VBP1
VBP2
VOUT
VBN1
IADD,P
IN2
IP2
VBN3
M39 M40M21 M22 M23 M41 M42
M24
M20
VSS
VDD
M37 M38
M25 M26
M32
M31
M35
M33
M36 M34
M27 M28 M29 M30
M4 M3
VDD
VSS
M2 M1 M7
M5 M6
M8
M10 M17
M11
M14
M13
M9
M18
M16
M15
M12
M19
core amplifierdynamic biasing circuit
Fig. 3 Proposed buffer amplifier with slew-rate enhancement throughout
entire rail-to-rail signal range
The rise slew rate is enhanced as follows. At steady state, the dynamic
biasing circuit does not affect the core amplifier. Because V
IP
and V
IN
have the same voltage, which puts M27, M28, M39 and M40 in the
triode region by appropriately sizing them, M29, M30, M41 and M42
are turned off. However, when the circuit enters the slewing state on a
sufficiently large rising step input at V
IP
, almost all of the tail current,
I
N2
, flows through M20, which is copied by M24, then M28 enters
the saturation region. Thus, the drain voltage of M28 becomes suffi-
ciently high to turn on M29, which enhances the slew rate by adding
the tail current for M1 and M2. For a falling step input signal, the
slew-rate enhancement is achieved in the same manner. M31 and M32
operate as a slew detector and enhance the slew rate by adding the tail
current for M3 and M4.
While this dynamic current source is based on those in [6] and [7],a
critical advantage of this design is provided by the rise and fall slew
detectors that employ NMOS (M19 and M20) and PMOS (M31 and
M32) transistors, respectively. Thus, unlike previous designs, the slew
detectors remain turned on even when the signals approach VDD or
VSS, and the slew rate is enhanced throughout the entire rail-to-rail
signal range.
Experimental results: The proposed buffer amplifier was fabricated in a
0.35 mm CMOS technology with 3.3 V supply. The amplifiers in [3]
and [7] were also fabricated on the same wafer for comparison purposes.
Fig. 4 shows the measured output waveforms of the amplifiers with
200 pF load capacitance. In Fig. 4a, the slew rate of [7] is enhanced
ELECTRONICS LETTERS 19th July 2012 Vol. 48 No. 15
compared with that of [3], but it becomes ineffective when the rising
signal reaches approximately 1 V below the VDD or the falling signal
reaches approximately 1 V above the VSS. In the proposed circuit, the
slew rate is enhanced throughout almost the entire rail-to-rail signal
range. The impact of the proposed circuit is more remarkable in
Figs 4band c. When the signal transits near VDD or VSS, slew-rate
enhancement is not observed with the circuit in [7], but the proposed
circuit obviously enhances the slew rate. In Fig. 4a, the overall slew
rate from VSS to VDD of the proposed circuit is enhanced from
0.49 V/
m
sin[3] and 0.80 V/
m
sin[7] to 2.75 V/
m
s. The quiescent
current of the proposed circuit is negligibly increased compared to
that of [7]. The quiescent current of the folded-cascode amplifier in
[3] ranges from 4.0 to 4.6 mA depending on the input common mode
voltage, and those of [7] and the proposed circuit are 4.3 to 5.1 mA
and 4.7 to 5.8 mA, respectively.
3
proposed
proposed
proposed
0V
2.5V
0V
2.5V
3.3V proposed
[3]
[7]
proposed
[3]
[7]
proposed
[3]
[7]
[7]
[7]
[7] [3]
0.8V
[3]
[3]
2ms
2ms
2ms
500mV
500mV
500mV
2
1
VOUT, v
0
3
2
1
VOUT, v
0
3
2
1
VOUT, v
0
024
3.3V
6810
a
b
c
12 14 16 18
0V
0 2 4 6 8 10 12 14 16 18
0246810
time, ms
12
0V
14 16 18
Fig. 4 Measured output waveforms from fabricated buffer amplifiers
aFrom VSS to VDD
bNear VDD
cNear VSS
Conclusion: A slew-rate-enhanced rail-to-rail buffer amplifier, which is
suitable for TFT LCD data drivers, is proposed. Unlike previous
counterparts, the slew rate is enhanced throughout the entire rail-to-
rail signal range. The measured slew rate from VSS to VDD of the pro-
posed circuit is enhanced from 0.49 V/
m
sin[3] and 0.80 V/
m
sin[7] to
2.75 V/
m
s with 200 pF load capacitance. The increase in the quiescent
current is negligible.
Acknowledgment: This work was supported by a National Research
Foundation of Korea grant funded by the Korean Government (NRF-
2011-013-D00077)
#The Institution of Engineering and Technology 2012
31 March 2012
doi: 10.1049/el.2012.0438
One or more of the Figures in this Letter are available in colour online.
J.S. Kim, J.Y. Lee and B.D. Choi (Department of Electronic
Engineering, Hanyang University, 222 Wangshimniro, Seongdong-gu,
Seoul 133-791, Republic of Korea)
E-mail: bdchoi@hanyang.ac.kr
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ELECTRONICS LETTERS 19th July 2012 Vol. 48 No. 15