High power factor electronic ballast using resonant converter for compact fluorescent lamp: Electronic Ballast Power Factor Correction Resonant Inverter

Abstract

This paper proposes a novel single stage single switch resonant inverter with high power factor for electronic ballast. The power factor correction circuit is at the input side. It is designed to operate at discontinuous conduction mode. The lamp power is controlled by adjusting the duty ratio of the active switch of the power factor correction circuit. The circuit operation is analyzed in detail to derive the design equations. Circuit parameters are designed based on design considerations. Finally, prototype electronic ballast for a 40-W compact fluorescent lamp is built and tested. The efficiency and the performance of the proposed converter are verified for the designed prototype.

Full text

High power factor electronic ballast using resonant converter for
compact fluorescent lamp
Geetha Ramadas
1
, Manoj Kumar Nadesan
1
, Sukhi Yesuraj
1,
*
,†
and Jeyashree Yesuraj
2
1
EEE Department, RMK Engineering College, Chennai, Tamilnadu, India
2
EEE Department, SRM University, Chennai, Tamilnadu, India
SUMMARY
This paper proposes a novel single stage single switch resonant inverter with high power factor for electronic
ballast. The power factor correction circuit is at the input side. It is designed to operate at discontinuous
conduction mode. The lamp power is controlled by adjusting the duty ratio of the active switch of the power
factor correction circuit. The circuit operation is analyzed in detail to derive the design equations. Circuit
parameters are designed based on design considerations. Finally, prototype electronic ballast for a 40-W
compact fluorescent lamp is built and tested. The efficiency and the performance of the proposed converter
are verified for the designed prototype. Copyright © 2016 John Wiley & Sons, Ltd.
Received 6 August 2015; Revised 2 May 2016; Accepted 5 May 2016
KEY WORDS: electronic ballast; high power factor; power factor correction; resonant inverter; energy
conversion; single stage single switch
1. INTRODUCTION
Lighting is an essential part of every household. From the beginning of invention of light, incandescent
lamps were used around the globe for illumination. Nowadays incandescent lamps neither are nor used
because of their poor efficiency. Recently, energy saving compact fluorescent lamps (CFLs) and light
emitting diode (LED) lamps used to reduce energy usage. At present replacement incandescent lamp
with LED lamps is the most energy efficient solution. But when cost is considered as key parameter,
the alternative replacement for incandescent lamp is CFLs [1–3]. The use of a microcontroller based
circuit provides several benefits over traditional analog control methods or commercially available
integrated circuits. In addition, these circuits have the advantages of high reliability and flexibility.
Noise immunity, resistance to environmental effects, possibility of changing the control scheme
without modifying the hardware and low cost are other attractive features of digital controllers [4].
The electromagnetic interference filter is designed to eliminate the harmonic components generated
by the high frequency switching of the power factor correction stage. Otherwise high frequency
harmonics can decrease the system power factor and cause interference problems with other
equipment [5]. In most of the lighting applications, the size of the lamp ballast is an important
factor. The size of the ballast should be as small as possible [6]. The bulky electromagnetic ballasts
are replaced by less weight, small size electronic ballasts because of its advantages [7]. The life of
the lamp can be prolonged by operating the switches with high frequency operation [8]. High
frequency operation reduces the size of the electronic ballast. The conventional two stage electronic
ballasts are replaced by single stage electronic ballasts by integrating power factor correction stage
and resonant inverter stage [9–18]. Most of the PFC stages associated with the aforementioned
†
INTERNATIONAL JOURNAL OF CIRCUIT THEORY AND APPLICATIONS
Int. J. Circ. Theor. Appl. (2016)
Published online in Wiley Online Library (wileyonlinelibrary.com). DOI: 10.1002/cta.2231
Tamilnadu 601206, India.
*Correspondence to: Manoj Kumar Nadesan, EEE Department, RMK Engineering College, Kavaraipettai, Chennai,
E-mail:nmk.eee@rmkec.ac.in
Copyright © 2016 John Wiley & Sons, Ltd.

ballasts operate in discontinuous conduction mode because feedback loops are not required for power
factor control.
The main problem of the two power processing circuits is the increasing the number of components
they require which corresponds to higher costs. To reduce costs, the single stage power processing
topologies combine with a dc–ac resonant inverter stage into one stage with sharing active switch,
making these single stage techniques attractive for commercial applications. In order to reduce the
number of switches used in the electronic ballast topology, single stage electronic ballasts have been
proposed [19–23]. However, the shared switch in single stage inverter with boost PFC suffers from
a high voltage stress. Zero voltage switching also improves the efficiency and reduces stress in the
devices [24–29]. The conventional high power factor circuit [7] is shown in Figure 1. It consists of
power factor correction circuit as the front end converter and a half bridge voltage fed resonant
inverter to control the lamp current. Even though this can achieve high power factor at the input, it
requires three MOSFETs in the power circuit [30, 31]. The resulting circuit has more losses and is
costly. In addition, the two stage approach lowers the power conversion efficiency. The single stage
single switch electronic ballast uses more number of inductors which results in more losses [32–34].
In paper [34], the input source supplies power to the lamp load through the input inductor L
in
.
While supplying power to the load, parallel tuned LC resonant circuit is used in between the source
and the load. In addition to series parallel resonant circuit, this circuit consists of parallel inductor
L
p
and parallel capacitor C
p
which are used to minimize the harmonics present at the output.
In the proposed converter, the input source supplies to the input inductor L
in
. The energy stored in
the inductor is supplied to the valley fill circuit and the load. This circuit provides a reduction of line
current THD. In this case the output power is dependent on the energy stored in the input inductor and
the valley fill capacitor. Therefore, this circuit does not require additional components to reduce
harmonics at the output. However, the main disadvantage is low efficiency because of high stresses
in the power switches and the use of more inductors in the circuit. In order to overcome this
disadvantage, this paper proposes new single stage single switch electronic ballast providing high
efficiency with less cost. The switches are operating with zero voltage switching which results in
zero switching losses with reduced stress and better efficiency. The large dc link capacitor is
eliminated to reduce stress and to improve power factor at all conditions.
The remainder of this paper is organized as follows. Section 2 presents circuit description of the
circuit. Section 3 presents the different modes of operation of the proposed converter. Section 4
presents the analysis of the proposed circuit to design power factor correction circuit element and
resonant circuit elements. The theoretical analysis of the proposed converter is verified using
experimental results in section 5. Conclusion is done in section 6.
2. CIRCUIT DESCRIPTION
The new proposed single stage power factor electronic ballast is shown in Figure 2. It consists of single
phase supply, power correction circuit formed by inductor L
in
, switch S antiparallel diode D, a resonant
Figure 1. Conventional electronic ballast.
G. RAMADAS ET AL.
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

tank consisting of an inductor L
s
, capacitor C
s
and parallel capacitor C
L
and capacitors C
1
,C
2
, diodes
D
2
,D
3
,D
4
and D
5
. The diode D
5
is acting as a freewheeling diode for the resonant converter. The duty
cycle is varied to vary the power input to the load. The power factor correction circuit is operated in
discontinuous conduction mode; thereby the input current naturally follows the sinusoidal waveform
of the input voltage. This results in unity power factor to the utility line. The proposed electronic
ballast switch consists of MOSFET and a parallel capacitor C. This arrangement let the current flow
in both the directions.
The newly designed circuit can be used for low and medium power. This paper is implemented to
improve the power factor of electronic ballast having series resonant inverter with zero switching
losses. The proposed resonant inverter is able to achieve zero switching losses during on and off
period. The inverter switches of the electronic ballast are operated at a switching frequency of
50 kHz. Because electronic ballast is inductive in nature, the inverter is connected to an inductive
load. The newly developed power factor correction circuit consists of an inductor L
in
which
guarantee discontinuous mode of operation and high power factor.
The input current flows through the inductor L
in
which acts as an energy conveyor from input source
to the load. The capacitors C
1
and C
2
serve as energy tank which processes input power sent to the load
by the diodes D
2
,D
3
and D
4
. These two capacitors are charged and discharged at high frequency which
results in small size capacitors. These capacitors are charging and discharging through diodes D
2
,D
3
,
D
4
and MOSFET switch S. When the current through the switch S becomes zero, the current in the
resonant circuit freewheels through the diode D
5
.
3. MODES OF OPERATION
The proposed converter circuit is designed to operate in discontinuous operation. The output voltage is
compared with the reference voltage set. Based on the error voltage, the gate voltages of the switches
are varied for constant voltage operation. The different modes of operation are described as follows.
3.1. Mode1
This mode of operation takes place during the time interval t
0
<t<t
1
.This mode begins at the instant of
turning ON of the switch S. The rectified input voltage is imposed on the inductor L
in
. Because the
converter is designed to operate at DCM, the inductor current i
L
increases linearly from zero with a
rising slope that is proportional to v
in
. Here zero current switching on of switch S is ensured. During
this interval, the energy stored in the resonant capacitor C
s
discharges through lamp, resonant
inductor L
s
, capacitors C
1
,C
2
and diode D
3
. This mode of operation ends when the resonant current
reaches zero. The circuit diagram of mode1 is shown in Figure 3.
3.2. Mode2
This mode of operation takes place during the time interval t
1
<t<t
2
. In this mode, the switch S
continues to be in on state. Because the resonant current direction is reversed at t
1
, diode D
3
is
reverse biased and stops conducting. The inductor current i
L
increases linearly till it reaches
maximum value. The capacitor energy bank C
1
and C
2
start discharging through diodes D
2
,D
4
,
Figure 2. Proposed electronic ballast.
ELECTRONIC BALLAST POWER FACTOR CORRECTION RESONANT INVERTER
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

lamp and resonant circuit till the switch S is turned off. This mode of operation ends when the switch S
is turned off at time t = t
2
. Because the voltage across the capacitor C is zero, zero voltage switching is
ensured. The circuit diagram of mode2 is shown in Figure 4.
3.3. Mode3
This mode of operation takes place during the time interval t
2
<t<t
3
.The circuit operation enters this
mode at the instant of turning off of switch S. The inductor current i
L
starts charging the capacitors C
1
and C
2
through diode D
3
and also supplies power to the lamp through resonant elements and diode D
1
.
This mode ends when the inductor current i
L
becomes zero. The circuit diagram of mode3 is shown in
Figure 5.
3.4. Mode4
This mode of operation takes place during the time interval t
3
<t<t
4
. In this mode, the switch S is in
off state. The energy stored in the resonant inductor L
s
free wheels through resonant capacitor C
s
, lamp
and diode D
5
. This mode of operation ends when the resonant current reaches zero. The circuit diagram
of mode4 is shown in Figure 6.
3.5. Mode5
This mode of operation takes place during the time interval t
4
<t<t
5
. During this mode, the switch S is
off state. The resonant capacitor C
s
starts supplying power to the load through capacitors C
1
,C
2
,
resonant inductor L
s
and diode D
3
. This mode ends when the switch S
1
is turned ON. The circuit
diagram of mode5 is shown in Figure 7. Figure 8 illustrates the theoretical waveforms for different
modes of operation.
4. CIRCUIT ANALYSIS
The main feature of this circuit operation is the discontinuous mode of operation. For simplifying the
circuit analysis, lamp is represented by its equivalent resistance R
L
. In the analysis all the circuit
components are considered as ideal. The ac line source voltage is given by
Figure 3. Mode1 (t
0
<t<t
1
).
Figure 4. Mode2 (t
1
<t<t
2
).
G. RAMADAS ET AL.
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

vstðÞ¼VmsinωLt(1)
where V
m
represents the amplitude of the input supply voltage and ω
L
represents the angular frequency
of the input source. In terms of the supply frequency, the angular frequency written as ω
L
=2πf
L
where
f
L
represents frequency of the voltage source. Practically, the line frequency is much lower than
switching frequency f
s
. It is reasonable to consider the rectified input voltage as a constant dc source
over a high frequency cycle. When the switch S is turned on, the inductor current i
L
(t) increases
linearly from zero and can be expressed as
iLtðÞ¼Vin tðÞ
Lin
t¼Vmsin 2πfLtðÞ
jj
Lin
t0≤t≤t2(2)
where t
2
can be written in terms duty ratio Dand switching period T
s
as t
2
=DT
s
.T
s
is the high-
frequency switching period and Dis the duty ratio of switch S. At the end of Mode2, i
L
(t) reaches
the maximum value at t
2
and is given by
Figure 5. Mode3 (t
2
<t<t
3
).
Figure 6. Mode4 (t
3
<t<t
4
).
Figure 7. Mode5 (t
4
<t<t
5
).
ELECTRONIC BALLAST POWER FACTOR CORRECTION RESONANT INVERTER
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

ILM ¼VmDTs
Lin
(3)
During mode3, the switch S is turned off. In this time interval t
2
<t<t
3
, the inductor current reaches
zero value. The energy stored in the inductor is transferred to the capacitors and the lamp when the
switch S is turned off. The capacitors C
1
and C
2
are considered to be of same value. In order to
have discontinuous operation for all values of duty ratio, the switch S is turned on again only after
the current has reached zero value.
Hence the expression for the discharging time when the inductor current reaches zero value is
given by
t3t2¼ILM Lin
2VC1
(4)
The waveform of the current i
L
(t) and I
Lm
are conceptually shown in Figure 9. Then, the input
current i
s
(t) is equal to the average of i
L
(t) over a high-frequency cycle.
Figure 8. Theoretical waveforms of proposed converter.
Figure 9. Waveform of i
L
(t) at high frequency.
G. RAMADAS ET AL.
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

iStðÞ¼ 1
TS
∫
TS
0
iLtðÞdt ¼VmTSD2
2Lin
sin 2πfLtðÞ (5)
When equations (1) and (5) are compared, it is noticed that the input current is a sinusoidal
waveform and in phase with the input line voltage. As a result, a unity power factor is achieved.
The input power can be obtained by taking average of its instantaneous value over one
line-frequency cycle.
PS¼1
2π
∫
2π
0
vStðÞiStðÞd2πfLtðÞ¼
V2
mD2
4LinfS
(6)
Now, the lamp power can be calculated using input power as below
Plamp ¼ηPS¼ηV2
mD2
4LinfS
(7)
where ηrepresents the circuit conversion efficiency. This expression shows that lamp power can be
regulated by varying the duty ratio. The voltage expression for a converter configuration to be in
discontinuous mode is
VC1≥Vm
2D
1D:(8)
Therefore the lamp power in terms of capacitor voltage is given by
Plamp ¼ηV2
C11DðÞ
2
LinfS
:(9)
Thus by varying the duty cycles, the output voltage can be varied below and above input voltage.
The main advantage of the resonant converter is that the sinusoidal nature of current and voltage
reduces the switching losses of the devices, and as a result the circuit can be operated at high
frequencies. When the tank circuit is operated at resonant frequency, very high current may be
delivered to the load.
Therefore, resonant circuits are operated either above or below the resonant frequency. The resonant
converters are based on resonant current oscillation. Because of the resonating components L
s
,C
L
, the
current through the devices falls to zero because of the natural characteristics of the circuit. This type of
circuit produces sinusoidal waveform at a high frequency. Because of the high switching frequency,
the size of components is small. The analysis of the resonant inverter can be performed based on the
equivalent circuit and its input voltage waveform shown in Figure 10(a) and 10(b) respectively. The
input to the resonant converter is a square voltage of frequency f
s
. The resonant circuit has the effect
of filtering the higher harmonics of voltages so that a sine wave current appears at the input to the
resonant circuit. The resonance circuit is analyzed using classical ac analysis. From Figure 10(a), the
impedance of the resonant circuit is
ZAB ¼jωsLsþRL1
jωsCL
RLþ1
jωsCL
(10)
where ω
s
is the switching frequency of the converter in rad/s. From the equivalent circuit of Figure 10
(a), the voltage transfer function is
ELECTRONIC BALLAST POWER FACTOR CORRECTION RESONANT INVERTER
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

Vlamp
VAB ¼1
1ωsLs
1
ωsCL

þj
1
ωsCL
RL
(11)
where V
AB
represents the rms value of fundamental sine wave of the input square wave of amplitude
V
C1
. The fundamental expression relating rms value V
AB
and the amplitude of square wave is given
below
VAB ¼2ffiffiffi
2
p
πVC1(12)
The quality factor of the load circuit is given by
QL¼ωrLs
RL¼1
ωrCLRL¼Z0
RL
(13)
On simplification of equation (11) gives
Vlamp
VC1¼1
π2
41ω
ω

2

þjωS
ωr1
QL
(14)
where
ωr¼1
ffiffiffiffiffiffiffiffiffiffi
LsCL
p(15)
Figure 10. (a) Equivalent circuit of resonant converter. (b) Input voltage applied to the resonant converter.
G. RAMADAS ET AL.
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

The lamp power can be expressed as
Plamp ¼4V2
C1
π4Rlamp 1þωs
ωr

2

2
þ1
QLωs
ωr

2(16)
The above analysis of the converter is used to design the converter.
5. EXPERIMENTAL RESULTS
The design considerations are outlined as follows. An electronic ballast for a 40-W, 230-V CFL is
illustrated as a design example. The input voltage is 230 V, 50 Hz. The switching frequency of the
inverter is 50 kHz. From equation (7), the lamp power can be regulated by adjusting D. The
Figure 11. Experimental setup for the proposed converter.
ELECTRONIC BALLAST POWER FACTOR CORRECTION RESONANT INVERTER
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

efficiency of lamp is taken as 95%. In order to ensure discontinuous conduction, the critical capacitor
voltage is taken as 162.5 V for D = 0.5. The value of L
in
is calculated to ensure discontinuous
conduction using equation (9) with V
C1
= 200 V, as 3.13 mH. The capacitance C
1
and C
2
are
calculated using ripple voltage expression as 4.7 μF. The lamp resistance can be calculated using the
specification as 591 Ω. ZVS operation is obtained because of the parallel capacitor C connected
Figure 12. Experimental results of waveforms of input current and voltage for V
m
= 300 V.
Figure 13. Experimental results of inductor and rectified input voltage for V
m
= 300 V.
Figure 14. Experimental results of resonant converter input voltage and input current for V
m
= 300 V.
G. RAMADAS ET AL.
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

across the switch. Therefore the ratio of switching frequency to resonant frequency is taken as 1.1.
Using equation (16), the value of Q
L
is calculated as 2.1. The values of C
L
and L
s
are calculated
using equation (13) and equation (15) as 3.3 nF and 3.6 mH respectively.
The value of C
s
is greater than C
L
. The value of C
s
is taken as 33 nF. The converter is designed to
handle a total power of 40 W. The prototype also has been designed and implemented for a CFL of
Figure 15. Experimental results of lamp voltage and lamp current for V
m
= 300 V.
Figure 16. Experimental results of switch voltage and lamp current for V
m
= 300 V.
Figure 17. Experimental results of lamp preheat and ignition voltage and lamp current.
ELECTRONIC BALLAST POWER FACTOR CORRECTION RESONANT INVERTER
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

40 W. The lamp is tested for various values of input voltage. In order to eliminate the harmonic
components generated by the high frequency switching of the power factor correction stage, the
electromagnetic interference filter is designed. Using thumb rule, inductance and capacitance of the
line filter are considered as L
m
= 2 mH and C
m
= 2 nF respectively. Figure 11 shows the experimental
setup for the proposed converter using microcontroller and the associated circuit. The control circuit
consists of microcontroller, analog to digital converter, opto-coupler, timer and crystal oscillator as
main elements. The output voltage is sensed and is applied to the analog to digital converter. Based
on the magnitude of the output voltage, the firing pulses are set for the MOSFET switches. The gate
pulses are given to switching devices through opto-coupler to separate the power circuit from
control circuit, and thus the control on the converter output is done. A small low pass filter
Figure 18. Efficiency of the converter versus input voltage.
Table I. Electronic input and output characteristics.
V
m
(V) I
m
(mA) P
in
(W) I
lampmax
(mA) V
lampmax
(V) P
0
(W) %ηpf
150 616.3 45.9 250.8 312.6 39.2 85.40 0.993
200 454.3 45.2 249.4 315.9 39.4 87.16 0.995
250 359.0 44.7 248.5 318.7 39.6 88.59 0.996
300 294.2 44.0 247.9 321.9 39.9 90.68 0.997
350 256.1 44.6 245.1 328.0 40.2 90.13 0.995
Table II. Comparison of recently reported topologies.
Reference paper Diodes Control switches Inductors Capacitors Input power factor Max ɳ
[5] 9 2 4 4 0.99–0.994 87%
[7] 10 2 3 4 0.996–0.998 NA
[17] 8 2 3 7 0.999 93.52%
[18] 8 2 3 9 0.999 90%
[11] 6 1 5 5 0.972 90.4%
[32] 7 1 5 4 0.996 83.4%
[33] 7 1 6 5 0.992 81.8%
proposed 9 1 3 5 0.993–0.997 90.68%
G. RAMADAS ET AL.
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

consisting of an inductor L
m
and a capacitor C
m
is used to remove the high frequency harmonics at the
input line in the experimental setup. Figure 12 shows experimental results of waveforms of input
current and voltage for a maximum input voltage of 325 V. The low pass filter is used at the input
side to remove the high frequency components. The input current is in phase with the input voltage
and is shown in Figure 12. Figure 13 shows the experimental results of waveforms of rectified input
current and inductor current. The switch is operating at high frequency. The current through the
resonant circuit and the input voltage across resonant circuit are shown in Figure 14. The resonant
current is sinusoidal in nature and flows through the lamp. The experimental results of voltage
across the lamp and the current flowing through electronic ballast are shown in Figure 15. The
voltage across the switch and current through the switch are shown in Figure 16. The voltage across
the lamp and the current through the lamp during preheat period and the ignition period are shown in
Figure 17.
The efficiency of the converter is measured for various values of input voltages and is shown in
Figure 18. The electronic ballast input and output characteristics obtained for various input voltage
are given in Table I. The results shown in Table I are obtained for various input voltages after the
introduction of power factor correction circuit and the energy tank circuit. With the introduction of
power factor correction circuit, the power factor is measured to be approximately 1. The efficiency
of the ballast with the introduction of power factor correction circuit and energy tank is 90.68%.
The comparison of recently reported topologies is given in Table II. Papers [5,7,11,17, 18] and the
proposed converter are implemented using LCC resonant inverter. Papers [32] and [33] are
constructed using LLC resonant inverter. Therefore from the table showing the comparison of
different topologies, it can be concluded that LCC resonant inverter is better than LLC resonant
inverter for electronic ballast. The results shown in Table II for the proposed converter are found to
be comparatively good and feasible. Table III gives the comparison of voltage stress developed
across the switches in the topologies discussed in the paper.
6. CONCLUSION
Novel electronic ballast has been designed using high frequency single stage single switch high power
factor resonant inverter. The elimination of large dc link capacitor has reduced stress and improved
power factor at all conditions. A small energy tank is introduced between the input supply and the
inverter stage to process the input power at high frequency. The size of the energy tank is made
small by operating the circuit at high frequency of operation. By properly selecting the circuit
parameters, approximately unit power factor is obtained. The additional power factor correction
circuit is made up of reactive elements which do not involve any power loss. The energy transfer
diodes and capacitors are used to transfer power. The switches are turned on and off softly which
results in zero switching losses. The number of switches in the inverter is reduced which results in
low cost electronic ballast. The experimental results show that a good efficient converter with less
cost can be obtained for CFL using the proposed circuit.
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ELECTRONIC BALLAST POWER FACTOR CORRECTION RESONANT INVERTER
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta

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ELECTRONIC BALLAST POWER FACTOR CORRECTION RESONANT INVERTER
Copyright © 2016 John Wiley & Sons, Ltd. Int. J. Circ. Theor. Appl. (2016)
DOI: 10.1002/cta