Figure 1 - uploaded by Sherief Hashima
Content may be subject to copyright.
Source publication
this book is suitable for undergraduate engineering students and it is related to electronic basics such as diodes, transistors, Mosfets, and CMOS
Contexts in source publication
Context 1
... we are interested only in the ac response of the circuit, all the dc supplies can be replaced by a zero-potential equivalent (short circuit) because they determine only the dc (quiescent level) of the output voltage and not the magnitude of the swing of the ac output. This is clearly demonstrated by Fig. 1.2. The dc levels were simply important for determining the proper Q -point of operation. Once determined, the dc levels can be ignored in the ac analysis of the network. In addition, the coupling capacitors C 1 and C 2 and bypass capacitor C 3 were chosen to have a very small reactance at the frequency of application. Therefore, they, ...
Context 2
... open circuit impedance characterization of two port network is shown in figure 1.5 known as impedance parameters. Its equations are ...
Context 3
... parameters relating the four variables are called h-parameters , from the word Because each term of hybrid parameters equations has the unit volt, let us apply Kirchhoff's voltage law "in reverse" to find a circuit that "fits" the equation. Performing this operation results in the circuit of Fig. 1.17. Because the parameter h 11 has the unit ohm, it is represented by a resistor in Fig. 1.17 . The quantity h 12 is dimensionless and therefore simply appears as a multiplying factor of the "feedback" term in the input circuit. Let us now apply Kirchhoff's current law "in reverse" to obtain the circuit of The complete "ac" equivalent ...
Context 4
... are called h-parameters , from the word Because each term of hybrid parameters equations has the unit volt, let us apply Kirchhoff's voltage law "in reverse" to find a circuit that "fits" the equation. Performing this operation results in the circuit of Fig. 1.17. Because the parameter h 11 has the unit ohm, it is represented by a resistor in Fig. 1.17 . The quantity h 12 is dimensionless and therefore simply appears as a multiplying factor of the "feedback" term in the input circuit. Let us now apply Kirchhoff's current law "in reverse" to obtain the circuit of The complete "ac" equivalent circuit for the basic three-terminal linear device is indicated in Fig. 1.17 with a new set ...
Context 5
... represented by a resistor in Fig. 1.17 . The quantity h 12 is dimensionless and therefore simply appears as a multiplying factor of the "feedback" term in the input circuit. Let us now apply Kirchhoff's current law "in reverse" to obtain the circuit of The complete "ac" equivalent circuit for the basic three-terminal linear device is indicated in Fig. 1.17 with a new set of subscripts for the h -parameters. The notation of Fig. 1 To distinguish which parameter has been used or which is available, a second subscript has been added to the h-parameter notation. For the common-base configuration, the lowercase letter b was added, whereas for the common-emitter and common-collector ...
Context 6
... therefore simply appears as a multiplying factor of the "feedback" term in the input circuit. Let us now apply Kirchhoff's current law "in reverse" to obtain the circuit of The complete "ac" equivalent circuit for the basic three-terminal linear device is indicated in Fig. 1.17 with a new set of subscripts for the h -parameters. The notation of Fig. 1 To distinguish which parameter has been used or which is available, a second subscript has been added to the h-parameter notation. For the common-base configuration, the lowercase letter b was added, whereas for the common-emitter and common-collector configurations, the letters e and c were added, ...
Context 7
... hybrid equivalent network for the common-emitter configuration appears with the standard notation in Figure 1.18 a, b. ...
Context 8
... that I i = I b , I o = I c , and, through with the output voltage V ce . For the common-base configuration of Figure 1.18 c, d. ...
Context 9
... the fixed-bias configuration of Fig.1.23, the small-signal ac equivalent network will appear as shown in Fig. 1.24 using the approximate common-emitter hybrid equivalent model. ...
Context 10
... the fixed-bias configuration of Fig.1.23, the small-signal ac equivalent network will appear as shown in Fig. 1.24 using the approximate common-emitter hybrid equivalent model. ...
Context 11
... the voltage-divider bias configuration of Fig. 1.26, the resulting small-signal ac equivalent network will have the same appearance as Fig. 1.23, with R B replaced by ...
Context 12
... the voltage-divider bias configuration of Fig. 1.26, the resulting small-signal ac equivalent network will have the same appearance as Fig. 1.23, with R B replaced by ...
Context 13
... the CE unbypassed emitter-bias configuration of Fig.1.27, the small-signal ac model will be the same as Fig. 1.28 ...
Context 14
... the CE unbypassed emitter-bias configuration of Fig.1.27, the small-signal ac model will be the same as Fig. 1.28 The analysis will proceed in the same manner. ...
Context 15
... the emitter-follower circuit of Fig. 1.29, the small-signal ac model resulting equations will therefore be quite similar For Z o , the output network defined by the resulting equations will appear as shown in ...
Context 16
... the emitter-follower circuit of Fig. 1.29, the small-signal ac model resulting equations will therefore be quite similar For Z o , the output network defined by the resulting equations will appear as shown in Fig.1.30. ...
Context 17
... last configuration to be examined with the approximate hybrid equivalent circuit will be the common-base amplifier of Fig. 1.31 . Substituting the approximate common- base hybrid equivalent model results in the network of Fig. 1.32 . ...
Context 18
... last configuration to be examined with the approximate hybrid equivalent circuit will be the common-base amplifier of Fig. 1.31 . Substituting the approximate common- base hybrid equivalent model results in the network of Fig. 1.32 . ...
Context 19
... the general configuration of Fig. 1.34 with the two-port parameters of particular interest. The complete hybrid equivalent model is then substituted in Fig. 1.35 using parameters that do not specify the type of configuration. In other words, the solutions will be in terms of h i , h r , h f , and h o . Here the current gain A i will be determined first because the ...
Context 20
... the general configuration of Fig. 1.34 with the two-port parameters of particular interest. The complete hybrid equivalent model is then substituted in Fig. 1.35 using parameters that do not specify the type of configuration. In other words, the solutions will be in terms of h i , h r , h f , and h o . Here the current gain A i will be determined first because the equations developed will prove useful in the determination of the other parameters. ...
Context 21
... that the basic equations for each quantity have been derived, the order in which they are calculated is arbitrary. However, the input impedance is often a useful quantity to know, and therefore will be calculated first. The complete common-emitter hybrid equivalent circuit has been substituted and the network redrawn as shown in Fig. 1 is often so high that it can be ignored compared to the applied load. However, keep in mind that when there is a need to determine the effect of h re and h oe , the complete hybrid equivalent model must be used, as described ...
Similar publications
A compilation of information regarding Malaysian Economy. This book, intended for undergraduate study, serves as one of the additional references for students with minimum exposure to Economics.
Exercise book for undergraduate students
